Pilot Symbol Generation for Highly-Spectrally-Efficient Communications

ABSTRACT

A transmitter may be operable to generate a sequence of symbols which may comprise information symbols and one or more pilot symbols. The transmitter may transmit the information symbols at a first power and transmit the one or more pilot symbols at a second power. In instances when a particular performance indicator is below a determined threshold, the first power may be set to a first value and the second power may be set to zero value. In instances when the particular performance indicator is above the determined threshold, the first power may be set to a second value and the second power may be set to a non-zero value. A value of the first power and a value of the second power may be based on an applicable average power limit determined by a communications standard with which the transmitter is to comply.

CROSS-REFERENCE TO RELATED APPLICATIONS/INCORPORATION BY REFERENCE

This patent application is a continuation of U.S. patent application Ser. No. 13/756,079 filed Jan. 31, 2013, now U.S. Pat. No. 8,665,992, and makes reference to, claims priority to, and claims benefit from:

U.S. Provisional Patent Application Ser. No. 61/662,085 entitled “Apparatus and Method for Efficient Utilization of Bandwidth” and filed on Jun. 20, 2012, now expired;

U.S. Provisional Patent Application Ser. No. 61/726,099 entitled “Modulation Scheme Based on Partial Response” and filed on Nov. 14, 2012, now expired;

U.S. Provisional Patent Application Ser. No. 61/729,774 entitled “Modulation Scheme Based on Partial Response” and filed on Nov. 26, 2012, now expired; and

U.S. Provisional Patent Application Ser. No. 61/747,132 entitled “Modulation Scheme Based on Partial Response” and filed on Dec. 28, 2012, now expired.

This application also makes reference to:

U.S. Pat. No. 8,582,637, titled “Low-Complexity, Highly-Spectrally-Efficient Communications,” and filed on Jan. 31, 2013;

U.S. patent application Ser. No. 13/754,998, titled “Design and Optimization of Partial Response Pulse Shape Filter,” and filed on Jan. 31, 2013;

U.S. Pat. No. 8,559,496, titled “Signal Reception Using Non-Linearity-Compensated, Partial Response Feedback,” and filed on Jan. 31, 2013;

U.S. Pat. No. 8,605,832, titled “Joint Sequence Estimation of Symbol and Phase with High Tolerance of Nonlinearity,” and filed on Jan. 31, 2013; and

U.S. patent application Ser. No. 13/755,052 titled “Pilot Symbol-Aided Sequence Estimation for Highly-Spectrally-Efficient Communications,” and filed on Jan. 31, 2013.

Each of the above referenced applications is hereby incorporated herein by reference in its entirety.

FIELD

Certain embodiments of the disclosure relate to communication systems. More specifically, certain embodiments of the disclosure relate to a method and system for pilot symbol generation for highly-spectrally-efficient communications.

BACKGROUND

Existing communications methods and systems are overly power hungry and/or spectrally inefficient. Complex linear modulation schemes such as, for example, quadrature amplitude modulation (QAM), are used vastly in wireless and non-wireless communications. However, performance of such modulation schemes degrades in the presence of phase noise and non-linear distortion associated with the communication channel. Some of these modulation schemes may perform, for example, 4-5 dB below the Shannon capacity bound in the case of severe phase noise. As higher-order modulation is needed to drive more throughput, the result may be a throughput that is even further away from the Shannon capacity limit. That is, the gap between desired spectral efficiency and actual spectral efficiency may actually increase with increasing QAM order. In addition, higher-order modulation may also be increasingly sensitive to non-linear distortion.

Further limitations and disadvantages of conventional and traditional approaches will become apparent to one of skill in the art, through comparison of such systems with the present disclosure as set forth in the remainder of the present application with reference to the drawings.

BRIEF SUMMARY OF THE DISCLOSURE

Aspects of the present disclosure are directed to a method and system for pilot symbol generation for highly-spectrally-efficient communications, substantially as shown in and/or described in connection with at least one of the figures, as set forth more completely in the claims.

Various advantages, aspects and novel features of the present disclosure, as well as details of an illustrated embodiment thereof, will be more fully understood from the following description and drawings.

BRIEF DESCRIPTION OF DRAWINGS

FIG. 1 is a block diagram illustrating an example communication system, in accordance with an embodiment of the disclosure.

FIG. 2A is a block diagram illustrating an example coupling of an equalizer and a sequence estimation module in a receiver, in accordance with an embodiment of the disclosure.

FIG. 2B is a block diagram illustrating an example sequence estimation module in a receiver, in accordance with an embodiment of the disclosure.

FIG. 3 is a diagram illustrating example pilot symbols, in accordance with an embodiment of the disclosure.

FIG. 4 is a flow chart illustrating example steps for pilot symbol generation for highly-spectrally-efficient communications, in accordance with an embodiment of the disclosure.

FIG. 5 is a flow chart illustrating example steps for pilot symbol generation for highly-spectrally-efficient communications, in accordance with an embodiment of the disclosure.

DETAILED DESCRIPTION

As utilized herein, “and/or” means any one or more of the items in the list joined by “and/or”. As an example, “x and/or y” means any element of the three-element set {(x), (y), (x, y)}. As another example, “x, y, and/or z” means any element of the seven-element set {(x), (y), (z), (x, y), (x, z), (y, z), (x, y, z)}. As utilized herein, the term “exemplary” means serving as a non-limiting example, instance, or illustration. As utilized herein, the terms “e.g.,” and “for example” set off lists of one or more non-limiting examples, instances, or illustrations. As utilized herein, a device/module/circuitry/etc. is “operable” to perform a function whenever the device/module/circuitry/etc. comprises the necessary hardware and code (if any is necessary) to perform the function, regardless of whether performance of the function is disabled, or not enabled, by some user-configurable setting.

Certain embodiments of the disclosure can be found in a method and system for pilot symbol generation for highly-spectrally-efficient communications. In various embodiments of the disclosure, a transmitter in a communication system may be operable to generate a sequence of symbols which may comprise information symbols and one or more pilot symbols. The transmitter may transmit the information symbols at a first power and transmit the one or more pilot symbols at a second power. In this regard, the second power may be set to zero value in instances when a particular performance indicator is below a determined threshold and to a non-zero value in instances when the particular performance indicator is above the determined threshold. In such instances, the first power may be set to a first value in instances when the particular performance indicator is below the determined threshold, and to a second value in instances when the particular performance indicator is above the determined threshold.

In an example embodiment of the disclosure, a value of the first power and a value of the second power may be based on an applicable average power limit determined by a communications standard with which the transmitter is to comply. The particular performance indicator may be a function based on phase noise and/or signal-to-noise ratio (SNR), for example. In this regard, the non-zero value of the second power may be determined, by the transmitter, based on a tradeoff between the phase noise and the SNR. The first power and the second power may be based on a tradeoff between phase noise tolerance and additive white Gaussian noise (AWGN) tolerance.

In an example embodiment of the disclosure, each of the one or more pilot symbols may be set to a known value in a modulation symbol constellation associated with the information symbols or in other modulation symbol constellation. For example, each of the information symbols may be set to a value in a quadrature amplitude modulation (QAM) symbol constellation, and each of the one or more pilot symbols may be set to a value in a lower order phase shift keying (PSK) symbol constellation. The one or more pilot symbols may be transmitted with a pseudo random pattern. The one or more pilot symbols may occur at deterministic times in the generated symbol sequence. The generated symbol sequence may comprise, for example, K consecutive pilot symbols every N information symbols, where K and N are each a positive integer. In this regard, for example, the generated symbol sequence may comprise two consecutive pilot symbols every forty information symbols. In other instances, the generated symbol sequence may comprise at least one information symbol between pilot symbols.

In an example embodiment of the disclosure, the transmitter may be operable to adapt a pilot rate of the one or more pilot symbols and a forward error correction (FEC) rate in presence of phase noise and AWGN, according to a specified overall rate budget for the pilot rate and the FEC rate. In this regard, the transmitter may be operable to adapt the pilot rate dynamically based on one or more performance indicators, for example.

FIG. 1 is a block diagram illustrating an example communication system, in accordance with an embodiment of the disclosure. Referring to FIG. 1, there is shown a communication system 100. The communication system 100 may comprise a transmitter 120, a communication channel 108 and a receiver 130. The transmitter 120 may comprise, for example, a mapper 102. The receiver 130 may comprise, for example, a sequence estimation module 112 and a de-mapper 114. A total partial response filtering function may be split between the transmitter 120 and the receiver 130. In this regard, the transmitter 120 may comprise a pulse shaper 104 and the receiver 130 may comprise an input filter 105. The total partial response filtering function may be split between the pulse shaper 104 and the input filter 105. In an example embodiment of the disclosure, other components such as, for example, a forward error correction (FEC) encoder in the transmitter 120, an interleaver in the transmitter 120, a timing recovery module in the receiver 130, a de-interleaver in the receiver 130, and/or a FEC decoder in the receiver 130 may also be optionally included without departing from the spirit and scope of various embodiments of the disclosure. For example, a FEC encoder (not shown) may be included to receive data bits input and generate code words including parity bits or parity words to enable error correction in the receiver 130. Output signals of the FEC encoder may be inputted to the mapper 102, for example. In this regard, a FEC decoder (not shown) may be included, for example, to receive signals from the de-mapper 114 and may be operable to utilize the parity bits or the parity words generated by the FEC encoder to correct bit errors. An overhead of the FEC may be referred to as a FEC code rate or FEC rate.

The mapper 102 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to input data bits and generate symbols according to, for example, a linear modulation scheme such as a quadrature amplitude modulation (QAM). In this regard, an M-QAM modulation scheme may comprise a total of M symbols in a QAM symbol constellation over an I-Q plane (M is a positive integer). For example, 32-QAM may comprise a total of 32 symbols in the 32-QAM symbol constellation. A modulation symbol constellation 150 is also illustrated in FIG. 1. Although M-QAM is used for illustration in this disclosure, aspects of this disclosure are applicable to any modulation scheme (e.g., amplitude shift keying (ASK), phase shift keying (PSK), frequency shift keying (FSK), etc.). Additionally, points of the M-QAM constellation may be regularly spaced (“on-grid”) or irregularly spaced (“off-grid”). In an example embodiment of the disclosure, the mapper 102 may be operable to insert one or more pilot symbols 140 (e.g., a particular pattern of pilot symbols 140) into a generated symbol sequence. In an example embodiment, the pilot symbol(s) 140 may be inserted in a deterministic manner (e.g., periodically and/or on an event-driven basis) such that a receiver 130 of the signal may know, or be able to autonomously determine, that the symbols are pilot symbols 140 and not information symbols (information symbols being symbols generated from data bits input to the mapper 102).

The pulse shaper 104 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to adjust the waveform of a signal received from the mapper 102 such that the waveform of a resulting signal complies with the spectral requirements of a communication channel such as the channel 108. The spectral requirements may be referred to as the “spectral mask” and may be established by a regulatory body (e.g., the Federal Communications Commission in the United States or the European Telecommunications Standards Institute) and/or a standard body (e.g., Third Generation Partnership Project) that governs the communication channels and/or standards in use.

The input filter 105 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to adjust the waveform of the signal received via the channel 108 to generate a signal for further processing in the receiver 130.

Each of the pulse shaper 104 and the input filter 105 may comprise, for example, an infinite impulse response (IIR) and/or a finite impulse response (FIR) filter. The number of taps in the pulse shaper 104 is designated LTx and the number of taps in the input filter 105 is designated LRx. The impulse response of the pulse shaper 104 is denoted herein as hTx and the impulse response of the input filter 105 is denoted herein as hTRx.

In an example embodiment of the disclosure, in order to improve tolerance of non-linearity, the pulse shaper 104 and the input filter 105 may be configured such that each of the output signal of the pulse shaper 104 and the output signal of the input filter 105 intentionally has a substantial amount of inter-symbol interference (ISI). In this regard, the ISI is therefore a controlled ISI. Accordingly, the pulse shaper 104 may be referred to as a partial response pulse shaping filter, and the resulting (output) signals of the pulse shaper 104 and the input filter 105 may be referred to as partial response signals or as residing in the partial response domain. The number of the taps and/or the values of the tap coefficients of the input filter 105 may be designed such that it is intentionally non-optimal in terms of noise in order to improve the tolerance of non-linearity. In this regard, the pulse shaper 104 and/or the input filter 105 in the system 100 may offer superior performance in the presence of non-linearity as compared to, for example, a conventional near zero positive ISI pulse shaping filter such as a raised cosine (RC) pulse shaping filter or a root-raised cosine (RRC) pulse shaping filter.

It should be noted that a partial response signal (or signals in the “partial response domain”) is just one example of a type of signal for which there is correlation among symbols of the signal (referred to herein as “inter-symbol-correlated (ISC) signals”). Such ISC signals are in contrast to zero (or near-zero) ISI signals generated by, for example, raised-cosine (RC) or root-raised-cosine (RRC) filtering. For simplicity of illustration, this disclosure focuses on partial response signals generated via partial response filtering. Nevertheless, aspects of this disclosure are applicable to other ISC signals such as, for example, signals generated via matrix multiplication (e.g., lattice coding), and signals generated via decimation as in multi carrier applications such as in OFDM systems.

A “total partial response (h)” may be equal to the convolution of hTx and hRx, and, thus, the “total partial response length (L)” may be equal to LTx+LRx−1. L may, however, be chosen to be less than LTx+LRx−1 where, for example, one or more taps of the pulse shaper 104 and/or the input filter 105 are below a determined level. Reducing L may reduce decoding complexity of a sequence estimation process in the receiver 130. This tradeoff may be optimized during the design of the pulse shaper 104 and the input filter 105 in the system 100.

The Tx media matching module 107 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to transform the partial response signal outputted by the pulse shaper 104 to an appropriate signal needed to drive the media in the channel 108. For example, the Tx media matching module 107 may comprise a power amplifier, a radio frequency (RF) up-converter, an optical transceiver for optical application, and/or other transformation device which may be required for propagating over the media.

The Rx media matching module 109 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to convert the signal coming from the media in the channel 108 to baseband signal for processing or demodulating. For example, the Rx media matching module 109 may comprise a power amplifier, a radio frequency (RF) down-converter, an optical transceiver for optical application, and/or other transformation device.

The channel 108 may comprise suitable logic, circuitry, device, interfaces and/or code that may be operable to transmit signals from the transmitter 120 to the receiver 130. The channel 108 may comprise a wired, wireless and/or optical communication medium. The channel 108 may comprise noise such as, for example, additive white Gaussian noise (AWGN). The channel 108 may also introduce distortions such as multipath and fading. In an example embodiment of the disclosure, signals transmitted over the channel 108 may include distortion such as, for example, phase noise and/or non-linear distortion. In this regard, for example, the channel 108 may receive signals from the transmitter 120 via a Tx media matching module 107 which transforms the partial response signal outputted by the pulse shaper 104 to an appropriate signal needed to drive the media in the channel 108. The receiver 130 may receive signals from the channel 108 via an Rx media matching module 109 which converts the signal coming from the media to baseband for demodulating. Both the Tx media matching module 107 and the Rx media matching module 109 may introduce distortion such as phase noise and non-linear distortion (and/or other non-idealities) caused by, for example, limited dynamic range of components. For example, in radio applications, frequency sources may be needed for up-converting the partial response signal outputted by the pulse shaper 104 from baseband to radio frequency (RF). The frequency sources may introduce phase noise which may distort the phase of the modulated signal. Non-linear distortion (e.g., 3^(rd) order) may be generated by elements such as, for example, mixers, power amplifiers, variable attenuators and/or baseband analog amplifiers.

The equalizer 110 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to perform equalization functions for the receiver 130. The equalizer 110 may be operable to process a signal received by the equalizer 110 to reduce, for example, ISI caused by the channel 108 between the transmitter 120 and the receiver 130. In an example embodiment of this disclosure, the input signal of the equalizer 110 may be an ISC signal such as a partial response signal received via the channel 108. In this regard, the output signal of the equalizer 110 may be a partial response signal where the ISI left in the output signal may be primarily the result of the pulse shaper 104 and/or the input filter 105 (there may be some residual ISI from multipath, for example, due to use of a least-mean-square (LMS) approach in the equalizer 110). In an example embodiment of the disclosure, the equalizer 110 may be adapted based on an error signal that may be generated in reference to a reconstructed signal (e.g., a reconstructed partial response signal) generated by the sequence estimation module 112.

The sequence estimation module 112 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to perform sequence estimation functions for the receiver 130. The output of the sequence estimation module 112 may be a best estimation as to the value of a corresponding transmitted symbol (and/or the corresponding transmitted information bits) generated by the mapper 102 in the transmitter 120. The estimated values may comprise soft-decision estimates, hard-decision estimates, or both. In an example embodiment of the disclosure, stability of the sequence estimation process, performed by the sequence estimation module 112, may be maintained even at low signal-to-noise ratio (SNR) through use of a pattern of one or more pilot symbols 140 inserted, by the mapper 102, between or among information symbols. When an estimated symbol value corresponding to a transmitted pilot symbol is outputted from the sequence estimation module 112, it may be removed from the estimated signal (e.g., by the de-mapper 114).

The de-mapper 114 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to input estimated symbols from the sequence estimation module 112 and generate recovered data bits according to, for example, a linear modulation scheme such as a M-QAM. Alternatively, or additionally, the de-mapper 114 may generate a soft output for each bit, referred as LLR (Log-Likelihood Ratio). The soft output bits may be used by a soft-decoding forward error corrector (e.g. a low-density parity check (LDPC) decoder). The soft output bits may be generated using, for example, a Soft Output Viterbi Algorithm (SOVA) or similar. Such algorithms may use additional information of the sequence decoding process including metrics levels of dropped paths and/or estimated bit probabilities for generating the LLR, where

${{{LLR}\; (b)} = {\log \; \left( \frac{P_{b}}{1 - P_{b}} \right)}},$

where P is the probability that bit b=1.

In operation, the mapper 102 in the transmitter 120 may be operable to generate a sequence of symbols which may comprise information symbols and one or more pilot symbols 140. The one or more pilot symbols 140 may be inserted by the mapper 102. The information symbols may be transmitted by the transmitter 120 via the Tx media matching module 107 at a first power and the one or more pilot symbols 140 may be transmitted at a second power. In this regard, the second power may be set to zero value in instances when a particular performance indicator is below a determined threshold and to a non-zero value in instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold. In such instances, the first power may be set to a first value in instances when the particular performance indicator below the determined threshold, and to a second value in instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold. The particular performance indicator may be, for example, a function based on phase noise and/or SNR.

The one or more pilot symbols 140 may comprise, for example, a pseudo random pattern so as to prevent any spurs in the spectral mask. The one or more pilot symbols 140 may occur at deterministic times in the generated symbol sequence such that the receiver 130 may autonomously determine which symbols are pilot symbols 140 and/or predict when pilot symbols 140 may arrive. Each of the one or more pilot symbols 140 may correspond to a point in the modulation symbol constellation 150, for example, associated with the information symbols. In this regard, each of the one or more pilot symbols 140 may be set to a known value in the modulation symbol constellation 150. In another example implementation, each of the one or more pilot symbols 140 may be set to a known value in other modulation symbol constellation. In this regard, for example, each of the information symbols may be set to a value in a QAM symbol constellation such as the modulation symbol constellation 150, and each of the one or more pilot symbols 140 may be set to a value in a lower order PSK (e.g., a quadrature phase shift keying (QPSK) or a binary phase shift keying (BPSK)) symbol constellation.

In an example embodiment of the disclosure, a pilot rate (e.g., referred to as the pilot overhead (POH) which may be specified as the percentage of all transmitted symbols that are pilot symbols 140) of the one or more pilot symbols 140 and a FEC rate may be adapted, by the mapper 102, in presence of phase noise and AWGN, according to a specified overall rate budget for the pilot rate and the FEC rate. In this regard, the pilot rate and pattern of the one or more pilot symbols 140 may be adapted, by the mapper 102, dynamically based on one or more performance indicators (e.g., SNR, symbol error rate (SER), bit error rate (BER), metrics levels calculated by the module 112, etc.) associated with the channel 108.

The generated symbol sequence may comprise, for example, K consecutive pilot symbols 140 every N information symbols (K and N are each a positive integer). For example, the generated symbol sequence may comprise two consecutive pilot symbols 140 every forty information symbols. In other instances, the generated symbol sequence may comprise, for example, at least one information symbol between pilot symbols 140.

The sequence estimation module 112 may be operable to generate estimates of transmitted symbols utilizing a sequence estimation process. The transmitted symbols, which may be generated by the mapper 102, may be received by the receiver 130 via the channel 108. For each of the information symbols, a corresponding one of the generated estimates may be selected from a first set of one or more values based on a search, and for each of the one or more pilot symbols 140, a corresponding one of the generated estimates may be selected from a second set of one or more values based on a predetermination. The second set of one or more values may comprise one or more symbol values predetermined as corresponding to the one or more pilot symbols 140. In this regard, the pilot symbols 140 may facilitate stability of the sequence estimation process. Because errors in the sequence estimation process may tend to occur in bursts, deterministic pilot symbols 140 may guide the sequence estimation process back to the proper path. There may be a mechanism, for example, in the sequence estimation module 112 to lock to the frequency of, and track the occurrence of, the pilot symbols 140.

FIG. 2A is a block diagram illustrating an example coupling of an equalizer and a sequence estimation module in a receiver, in accordance with an embodiment of the disclosure. Referring to FIG. 2A, there is shown the equalizer 110 and the sequence estimation module 112. The sequence estimation module 112 may incorporate a non-linear model 210 in a sequence estimation process. The equalizer 110 and the sequence estimation module 112 may be as described with respect to FIG. 1, for example.

In the exemplary embodiment of the disclosure illustrated in FIG. 2A, although the equalizer 110 and the sequence estimation module 112 are shown, the disclosure may not be so limited. Other modules (or circuits) such as, for example, a carrier recovery module, a phase adjust module and/or other similar modules may also be optionally included in FIG. 2A without departing from the spirit and scope of various embodiments of the disclosure. For example, the carrier recovery module and/or the phase adjust module may be included for various phase correction or recovery throughout the equalization process and/or the sequence estimation process.

The non-linear model 210 may comprise, for example, a saturated third order polynomial which may be expressed as

$\begin{matrix} {y = \left\{ {{\begin{matrix} {{x \cdot \left( {1 - {r \cdot ^{j\; \phi} \cdot {x}^{2}}} \right)},} & {x < x_{sat}} \\ y_{{sat},} & {x \geq x_{sat}} \end{matrix}y_{sat}} = {x_{sat} \cdot \left( {1 - {r \cdot ^{j\; \phi} \cdot {x_{sat}}^{2}}} \right)}} \right.} & \lbrack 1\rbrack \end{matrix}$

where, x_(sat) denotes the input saturation value, y_(sat) denotes the output saturation value, x denotes an input of a non-linear device (or group of devices), y denotes an output of the non-linear device (or group of devices), and y may be set according to a desired distortion level (backoff). For example, the non-linear device may be a power amplifier in the Tx media matching module 107. In this regard, the x in equation [1] may denote an input power level of the power amplifier and the y may denote an output power level of the power amplifier. Increased accuracy resulting from the use of a higher-order polynomial for the non-linear model 210 may tradeoff with increased complexity of implementing a higher-order polynomial. As transmitter's non-linearity may be the dominant non-linearity of the communication system 100, modeling the transmitter's non-linearity may be sufficient. In instances where degradation in a receiver's performance is above a certain threshold due to other non-linearities in the system (e.g., non-linearity of the Rx media matching module 109), the non-linear model 210 may take into account such other non-linearities. Equation 1 represents just one example of a non-linearity model that may be used by the module 112 in one or more embodiments of the disclosure.

In an example operation, the equalizer 110 may be operable to process or equalize a signal 201 to reduce, for example, ISI caused by the channel 108. The equalizer adaptation may be based on, for example, a LMS algorithm. An error signal 205 is fed back to the equalizer 110 to drive the adaptive equalizer 110. The reference for generating the error signal 205 may be, for example, a reconstructed signal 203 coming from the sequence estimation module 112. In an example embodiment of the disclosure, the signal 201 may be an ISC signal such as a partial response signal. In this regard, the reconstructed signal 203 may be a reconstructed partial response signal. The error signal 205 is the difference, calculated by a combiner 204, between an output signal 202 of the equalizer 110 and the reconstructed signal 203. Generation of the reconstructed signal 203 may incorporate the non-linear model 210 of the signal 201 and is described below with reference to FIG. 2B. An equalized signal 230 may be inputted to the sequence estimation module 112. The sequence estimation module 112 may be operable to generate symbols (estimated symbols) 240, from the signal 230, using the sequence estimation process. The generated symbols 240 may be hard and/or soft estimates of transmitted symbols generated by the mapper 102 in the transmitter 120. An example implementation of the sequence estimation module 112 is described below with reference to FIG. 2B.

FIG. 2B is a block diagram illustrating an example sequence estimation module in a receiver, in accordance with an embodiment of the disclosure. Referring to FIG. 2B, there is shown the sequence estimation module 112. The sequence estimation module 112 may comprise, for example, a symbol candidate generation module 202, a metrics calculation module 204, a symbol survivor selection module 206, a symbol estimation module 220 and a signal reconstruction module 224. The sequence estimation process described with respect to FIG. 2B is an example only. Many variations of the sequence estimation process may also be possible. The sequence estimation module 112 may be as described with respect to FIGS. 1 and 2A, for example.

The metrics calculation module 204 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to generate metrics needed for symbol survivor selections and symbol (including corresponding phase) estimations. Metrics calculations may be executed based on a signal 230 received by the metrics calculation module 204 and symbol candidates generated by the symbol generation module 202. Each symbol candidate may be a vector comprising, for example, Q candidate symbols (Q is a positive integer). Information associated with the taps of the pulse shaper 104 and/or the input filter 105 may also be utilized for the metrics calculation. In an example embodiment of the disclosure, the signal 230 may be an ISC signal such as a partial response signal received from the input filter 105. The taps information (e.g., number of taps and/or tap coefficients) associated with the pulse shaper 104 and/or the input filter 105 may be used to generate reconstructed partial response signal candidates from the symbol candidates, for example, via convolution. The taps information associated with the pulse shaper 104 and/or the input filter 105 may be presented, for example, in the form of L (where LTx<=L<=(LTx+LRx−1)) tap coefficients corresponding to the total partial response h, according to the LTx tap coefficients of the pulse shaper 104 and the LRx tap coefficients of the input filter 105. Furthermore the non-linear model 210 may be incorporated in the process of generating the reconstructed partial response signal candidates. For example, the non-linear model 210 may be applied to the convolved symbol candidates to generate the reconstructed partial response signal candidates. The metric value for each of the symbol candidates may then be generated based on a cost function (e.g., a squared error function) between the signal 230 and the reconstructed partial response signal candidates. The candidates which have the best metrics level may be selected by the symbol survivor selection module 206 for the next iteration of the sequence estimation process.

The symbol survivor selection module 206 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to perform metrics sorting and selection of a determined number of symbol survivors based on the metrics associated with the symbol candidates. In this regard, for example, one or more candidates which have the lowest metrics level may be selected, from among the symbol candidates, as symbol survivors. Each symbol survivor may also be a vector comprising, for example, Q candidate symbols (Q is a positive integer). Each element of each symbol survivor may comprise a soft-decision estimate and/or a hard-decision estimate of a symbol of the signal 230. Besides a newly-detected symbol at a head of the vector, there are (Q-1) symbols in the vector. Some of the (Q-1) symbols could be different than corresponding symbols in a previously-selected symbol survivor (i.e. the sequence estimation may diverge to a different vector). The reliability of the newly-detected symbol may be very low because it may be derived only from the newest signal sample and a first tap of the L taps associated with the pulse shaper 104 and/or the input filter 105, which may have a coefficient that is small in magnitude. The reliability of old symbols toward a tail of the vector may improve along the survived vectors because old symbols are represented by many signal samples (up to effective number of the taps of the total partial response) and thus take advantage of more information. In this regard, the tails (old symbols) of the symbol survivors may converge to the same solution while the head (young symbols) parts of the symbol survivors may be different.

The symbol candidate generation module 202 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to generate symbol candidates from symbol survivors generated from a previous iteration of the sequence estimation process. For example, for M-OAM (M is a positive integer), there are M symbols in the M-QAM symbol constellation (e.g., the modulation symbol constellation 150) over an I-Q plane. In this regard, generation of the symbol candidates may comprise, for example, duplicating (e.g., (M-1) times) each of the symbol survivors (vectors) generated during the previous iteration of the sequence estimation process, shifting each of the resulting M vectors by one symbol position toward the tail of the vector, and then filling each of the M vacant symbol positions (at the head of the vector) with a symbol from among the M possible symbols in the M-QAM symbol constellation (e.g., the modulation symbol constellation 150).

In an example embodiment of the disclosure, the symbol candidate generation module 202 may be operable to eliminate search for an estimated symbol at a time when one of the pilot symbols 140 reaches a search location (i.e., when the symbol for which candidates are to be generated is a pilot symbol). That is, the estimated symbol at the search location may simply be determined to be the deterministic pilot symbol. In such instances, each of the symbol survivors (vectors) generated from the previous selection iteration may simply be shifted by one symbol position toward the tail of the vector, and the vacant symbol position may be filled with the one known pilot symbol. In an alternate implementation, a location of search (i.e., the element of the symbol candidate for which the metric is calculated) for an estimate of a transmitted symbol may be shifted, by the symbol candidate generation module 202, to be before or after a location holding one of the one or more pilot symbols 140. In such an alternate implementation, the number of candidates generated by the symbol candidate generation module 202 may be the same number of candidates as when the search is performed on the default location (the location now occupied by a pilot symbol). In this manner, shifting the search location to before the pilot symbols 140 may provide an opportunity to restore a good symbol survivor (e.g., symbol survivor with a metric below a threshold) that had been discarded in a previous iteration of the sequence estimation.

The symbol estimation module 220 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to generate symbols (estimated symbols) 240 based on the symbol survivors received from the symbol survivor selection module 206. The generated symbols 240 may be estimates of transmitted symbols generated by the mapper 102 in the transmitter 120. In an example embodiment of the disclosure, the symbol estimation module 220 may be operable to generate the estimated symbols 240 based on a best symbol survivor with the lowest metric value. The symbol estimation module 220 may comprise one or more buffers to store one or more symbol survivors.

The signal reconstruction module 224 may comprise suitable logic, circuitry, interfaces and/or code that may be operable to generate the reconstructed signal 203. In an example embodiment of the disclosure, the signal 230 may be an equalized ISC signal such as a partial response signal received from the equalizer 110. The taps information associated with the pulse shaper 104 and/or the input filter 105 (e.g., the L tap coefficients) may be used to generate the reconstructed signal (partial response signal) 203 from the estimated symbols 240, for example, via convolution. In this regard, for example, the non-linear model 210 may be incorporated in the process of generating the reconstructed signal (partial response signal) 203. For example, the non-linear model 210 may be applied to the convolved symbols to generate the reconstructed signal (partial response signal) 203.

In operation, the metrics calculation module 204 may be operable to receive, via the channel 108, the signal 230. The estimates (the estimated symbols 240) of transmitted symbols in the signal 230 may be generated by the sequence estimation module 112 utilizing a sequence estimation process. In this regard, the sequence estimation process may be performed by the metrics calculation module 204, the symbol candidate generation module 202, the symbol survivor selection module 206 and the symbol estimation module 220. The sequence estimation module 112 may be operable to maintain stability of the sequence estimation process based on the one or more pilot symbols 140. In this regard, for each of the information symbols, a corresponding one of the generated estimates may be selected from a first set of one or more values based on a symbol value search (performed by the symbol candidate generation module 202, the metrics calculation module 204 and the symbol survivor selection module 206). On the other hand, for each of the one or more pilot symbols 140, a corresponding one of the generated estimates may be selected from a second set of one or more values based on a predetermination. In this regard, for example, the symbol candidate generation module 202 may be operable to eliminate search for an estimated symbol at a time when one of the pilot symbols 140 reaches a search location. The estimated symbol at the search location may then be determined, for example, by the symbol candidate generation module 202, to be the known (predetermined) pilot symbol that reaches the search location, without need for candidate generation, etc. This may free-up resources of the sequence estimation module 112 to estimate the value of other symbols, and/or may allow time to perform an iterative process. For example, during an iteration of the sequence estimation process in which the most recently received symbol is a pilot symbol, the sequence estimation module 112 may perform a second estimation of a previous symbol whose metrics might be low (e.g., lower than a threshold and/or lower than metrics for other recently received symbols). This insertion of the pilot symbols 140 may also improve the sequence estimation reliability for other symbols because there may be less unknown symbols to estimate. Thus insertion of the pilot symbols 140 may improve noise (e.g., AWGN) tolerance and bit error rate (BER) performance. When the sequence estimation process is unstable and generates a long error burst or goes out of convergence, the pattern of pilot symbols 140 may be able to stop the error burst and may guide the sequence estimation process back to a stable state.

Alternately, the symbol candidate generation module 202 may be operable to shift a location of search for an estimate of a transmitted symbol to be before or after a location holding one of the one or more pilot symbols 140. Such an alternate implementation may provide an opportunity to restore a good symbol survivor that had been discarded in a previous iteration of the sequence estimation.

FIG. 3 is a diagram illustrating example pilot symbols, in accordance with an embodiment of the disclosure. Referring to FIG. 3, there is shown a best symbol survivor 300. The best symbol survivor 300 may comprise a plurality of information symbols 304 and a pattern of pilot symbols 140. The length of the best symbol survivor 330 may be determined or designed, for example, based on the total partial response length L (where LTx<=L<=(LTx+LRx−1)). For example, the length of the best symbol survivor 300 may be five times the length of the total partial response length L. There is also shown in FIG. 3 a best symbol survivor 300 comprising a pattern of pilot symbols 306 each configured to comprise zero power. There is also shown in FIG. 3 a best symbol survivor 300 comprising a pattern of pilot symbols 308 each configured to comprise a particular, non-zero power.

In an example operation, the estimated symbols 240 (estimates of transmitted symbols) may be generated, by the symbol estimation module 220, based on the best symbol survivor 300 generated in a sequence estimation process. The transmitted symbols may comprise information symbols 304 and a pattern of pilot symbols 104. In this regard, the best symbol survivor 300 may comprise a pattern of pilot symbols 140 and estimates of a plurality of information symbols 304. In an example embodiment of the disclosure, due to the convolution nature of the sequence estimation process for partial response modulated signals, it may be more effective to insert K consecutive pilot symbols 140 every N information symbols 304 (K and N are each a positive integer) generated and transmitted by the mapper 104. In this regard, the pilot symbols 140 may appear in the best symbol survivor 300 such that there are K consecutive pilot symbols 140 every N information symbols 304 (e.g., two consecutive pilot symbols 140 every forty information symbols 304).

The pilot symbols may be configurable. For example, power of each of the pilot symbols 306 may be zero power. In such instances, although the pilot symbols 306 may each comprise zero power, they may still possess information for the sequence estimation process and the sequence estimation may instead be utilized for determining or estimating the information symbols 304 (non-pilot symbols). In other instances, the pilot symbols such as the pilot symbols 308 may each comprise a particular, non-zero power which may be determined based on a tradeoff between phase noise and SNR associated with the transmitted symbols. In this regard, with the presence of zero-power pilot symbols 306, the power of each of the information symbols 304 may be increased comparing to the case with no pilot symbols or the case with non-zero-power pilot symbols 308. That is, because communication standards typically dictate a maximum average power, use of zero-power pilot symbols 306 that do not contribute to the average power enables information symbols to be slightly higher power and still remain within the applicable average power limit determined by a spectral mask and/or communications standard with which the transmitter 120 is to comply.

Non-zero-power pilot symbols 308 may consume power from the information symbols 304 (non-pilot symbols), but may be more effective in some instances such as, for example, in the presence of severe phase noise. For example, the transmitter 120 may measure phase noise, and/or receive a measurement of phase noise from the receiver 130, and may select the power of the pilot symbols 140 accordingly (e.g., phase noise below a threshold may result in use of zero-power pilot symbols 360 and phase noise above the threshold may result in use of non-zero-power pilot symbols 308). Therefore, the pilot symbol power may be a tradeoff between tolerance level of phase noise and tolerance level of AWGN (i.e., higher-power pilot symbols 308 may result in better phase noise tolerance but also necessitate lower power for information symbols 304, which may result in less tolerance of AWGN). Therefore, based on a tradeoff between phase noise tolerance and AWGN tolerance, and within the applicable average power limit, the information symbol 304 may be transmitted by the transmitter 120 via the Tx media matching module 107 at a first power and the one or more pilot symbol 140 may be transmitted at a second power.

In an example embodiment of the disclosure, the second power (the power of the pilot symbols such as the pilot symbols 306) may be set to zero value in instances when a particular performance indicator is below a determined threshold. The second power (the power of the pilot symbols such as the pilot symbols 308) may be set to a non-zero value in instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold. In such instances, the first power (the power of the information symbols 304) may be set to a first value in instances when the particular performance indicator is below the determined threshold, and to a second value in instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold. In this regard, the particular performance indicator may be a function based on the phase noise and/or the SNR. A value of the first power and a value of the second power may be based on an applicable average power limit determined by a spectral mask and/or communications standard with which the transmitter 120 is to comply. The transmitter 120, via the Tx media matching module 107, may be operable to determine the non-zero value of the second power based on a tradeoff between the phase noise and the SNR, for example. The first power and the second power may be based on a tradeoff between phase noise tolerance and AWGN tolerance, and/or any other suitable performance indicator.

FIG. 4 is a flow chart illustrating example steps for pilot symbol generation for highly-spectrally-efficient communications, in accordance with an embodiment of the disclosure. Referring to FIG. 4, the example steps start at step 401. In step 402, the mapper 102 in the transmitter 120 may be operable to generate a sequence of symbols which may comprise information symbols 304 and one or more pilot symbols 140. In step 403, the transmitter 120 may be operable to transmit, via the Tx media matching module 107, the information symbols 304 at a first power. In step 404, the transmitter 120 may be operable to transmit, via the Tx media matching module 107, the one or more pilot symbols 140, 306, 308 at a second power. In this regard, the second power may be set to zero value in instances when a particular performance indicator is below a determined threshold, and to a non-zero value in instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold. In this regard, the particular performance indicator may be, for example, a function based on phase noise and/or SNR. The example steps may proceed to the end step 405.

FIG. 5 is a flow chart illustrating example steps for pilot symbol generation for highly-spectrally-efficient communications, in accordance with an embodiment of the disclosure. Referring to FIG. 5, the example steps start at step 501. In step 502, the mapper 102 in the transmitter 120 may be operable to generate a sequence of symbols which may comprise information symbols 304 and one or more pilot symbols 140. In step 503, the transmitter 120 may be operable to transmit, via the Tx media matching module 107, the information symbols 304 at a first power. In step 504, the transmitter 120 may be operable to transmit, via the Tx media matching module 107, the one or more pilot symbols 140, 306, 308 at a second power. In this regard, in instances when a particular performance indicator is below a determined threshold, the first power may be set to a first value and the second power may be set to zero value. In instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold, the first power may be set to a second value and the second power may be set to a non-zero value. In this regard, the particular performance indicator may be, for example, a function based on phase noise and/or SNR. The example steps may proceed to the end step 505.

In various embodiments of the disclosure, a mapper 102 in a transmitter 120 may be operable to generate a sequence of symbols which may comprise information symbols 304 and one or more pilot symbols 140. The transmitter 120 may transmit, via a Tx media matching module 107, the information symbols 304 at a first power and transmit the one or more pilot symbols 140 at a second power. In this regard, the second power may be set to zero value in instances when a particular performance indicator is below a determined threshold and to a non-zero value in instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold. In such instances, the first power may be set to a first value in instances when the particular performance indicator is below the determined threshold, and to a second value in instances when the particular performance indicator is above (and in some embodiments, or equal to) the determined threshold. In this regard, the particular performance indicator may be, for example, a function based on phase noise and/or SNR.

A value of the first power and a value of the second power may be based on an applicable average power limit determined by a spectral mask and/or communications standard with which the transmitter 120 is to comply. The transmitter 120, via the Tx media matching module 107, may be operable to determine the non-zero value of the second power based on a tradeoff between the phase noise and the SNR, for example. The first power and the second power may be based on a tradeoff between phase noise tolerance and AWGN tolerance.

Each of the one or more pilot symbols 140 may be set to a known value in a modulation symbol constellation 150 associated with the information symbols 304 or in other modulation symbol constellation. For example, each of the information symbols may be set to a value in a QAM symbol constellation, and each of the one or more pilot symbols 140 may be set to a value in a lower order PSK (e.g., a QPSK or a BPSK) symbol constellation. The one or more pilot symbols 140 may be transmitted with a pseudo random pattern. The one or more pilot symbols 140 may occur at deterministic times in the generated symbol sequence. The generated symbol sequence may comprise, for example, K consecutive pilot symbols 140 every N information symbols 304, where K and N are each a positive integer. In this regard, for example, the transmitted symbols may comprise two consecutive pilot symbols 140 every forty information symbols 304. In other instances, the generated symbol sequence may comprise at least one information symbol between pilot symbols 140.

The mapper 102 in the transmitter 120 may be operable to adapt a pilot rate of the one or more pilot symbols 140 and a FEC rate in presence of phase noise and AWGN, according to a specified overall rate budget for the pilot rate and the FEC rate. In this regard, for example, the mapper 102 may be operable to adapt the pilot rate dynamically based on one or more performance indicators (e.g., SNR, SER, BER, metrics levels etc.).

Other embodiments of the disclosure may provide a non-transitory computer readable medium and/or storage medium, and/or a non-transitory machine readable medium and/or storage medium, having stored thereon, a machine code and/or a computer program having at least one code section executable by a machine and/or a computer, thereby causing the machine and/or computer to perform the steps as described herein for pilot symbol generation for highly-spectrally-efficient communications.

Accordingly, aspects of the present disclosure may be realized in hardware, software, or a combination of hardware and software. Aspects of the present disclosure may be realized in a centralized fashion in at least one computer system or in a distributed fashion where different elements are spread across several interconnected computer systems. Any kind of computer system or other apparatus adapted for carrying out the methods described herein is suited. A typical combination of hardware and software may be a general-purpose computer system with a computer program that, when being loaded and executed, controls the computer system such that it carries out the methods described herein.

Aspects of the present disclosure may also be embedded in a computer program product, which comprises all the features enabling the implementation of the methods described herein, and which when loaded in a computer system is able to carry out these methods. Computer program in the present context means any expression, in any language, code or notation, of a set of instructions intended to cause a system having an information processing capability to perform a particular function either directly or after either or both of the following: a) conversion to another language, code or notation; b) reproduction in a different material form.

While the present disclosure has been described with reference to certain embodiments, it will be understood by those skilled in the art that various changes may be made and equivalents may be substituted without departing from the scope of the present disclosure. In addition, many modifications may be made to adapt a particular situation or material to the teachings of the present disclosure without departing from its scope. Therefore, it is intended that the present disclosure not be limited to the particular embodiment disclosed, but that the present disclosure will include all embodiments falling within the scope of the appended claims. 

1-21. (canceled)
 21. A method, comprising: in a transmitter: generating a sequence comprising one or more pilot symbols and one or more information symbols; transmitting said sequence using a first transmit power setting for said one or more pilot symbols and a second transmit power setting for said one or more information symbols, such that an average power of said transmitted sequence complies with a particular spectral mask; determining phase noise and additive white Gaussian noise present in a received version of said transmitted sequence; in response to said determined phase noise and additive white Gaussian noise, concurrently adjusting said first transmit power setting and said second transmit power setting to achieve a desired balance between phase noise tolerance and additive white Gaussian noise tolerance.
 22. The method of claim 21, wherein said concurrently adjusting said first transmit power setting and said second power setting comprises increasing said first transmit power and decreasing said second transmit power when said determined phase noise phase noise is above a determined threshold.
 23. The method of claim 21, wherein said concurrently adjusting said first transmit power setting and said second power setting comprises decreasing said first transmit power and increasing said second transmit power when said determined phase noise phase noise is below a determined threshold.
 24. The method of claim 21, wherein said concurrently adjusting said first transmit power setting and said second power setting comprises increasing said first transmit power and decreasing said second transmit power when said determined additive white Gaussian noise is below a determined threshold.
 25. The method of claim 21, wherein said concurrently adjusting said first transmit power setting and said second power setting comprises decreasing said first transmit power and increasing said second transmit power when said determined additive white Gaussian noise is above a determined threshold.
 26. The method of claim 21 wherein said determining said phase noise and additive white Gaussian noise present in said received version of said transmitted sequence comprises receiving one or more measurements from a receiver that received said transmitted sequence.
 27. The method of claim 21, wherein said generating said sequence comprises inserting said one or more pilot symbol at pseudorandom intervals among said one or more information symbols.
 28. The method of claim 21, wherein said sequence comprises K consecutive pilot symbols every N information symbols, where K and N are each a positive integer greater than one.
 29. The method of claim 21, comprising: during said generating said sequence, determining how many of said one or more pilot symbols to insert in said sequence based on one or more performance indicators from a receiver to which said sequence is to be transmitted.
 30. The method of claim 29, wherein said one or more performance indicators comprise signal-to-noise ratio.
 31. A system, comprising: a transmitter comprising: circuitry operable to generate a sequence comprising one or more pilot symbols and one or more information symbols; circuitry operable to transmit said sequence using a first transmit power setting for said one or more pilot symbols and a second transmit power setting for said one or more information symbols such that an average power of said transmitted sequence complies with a particular spectral mask; circuitry operable to determine phase noise and additive white Gaussian noise present in a received version of said transmitted sequence; circuitry operable to, in response to said determined phase noise and additive white Gaussian noise, concurrently adjust said first transmit power setting and said second transmit power setting to achieve a desired balance between phase noise tolerance and additive white Gaussian noise tolerance.
 32. The system of claim 31, wherein said concurrent adjustment of said first transmit power setting and said second power setting comprises an increase of said first transmit power and decrease of said second transmit power when said determined phase noise phase noise is above a determined threshold.
 33. The system of claim 31, wherein said concurrent adjustment of said first transmit power setting and said second power setting comprises a decrease of said first transmit power and increase of said second transmit power when said determined phase noise phase noise is below a determined threshold.
 34. The system of claim 31, wherein said concurrent adjustment of said first transmit power setting and said second power setting comprises an increase of said first transmit power and decrease of said second transmit power when said determined additive white Gaussian noise is below a determined threshold.
 35. The system of claim 31, wherein said concurrent adjustment of said first transmit power setting and said second power setting comprises a decrease of said first transmit power and increase of said second transmit power when said determined additive white Gaussian noise is above a determined threshold.
 36. The system of claim 31 wherein said determination of said phase noise and additive white Gaussian noise present in said received version of said transmitted sequence comprises a reception of one or more measurements from a receiver that received said transmitted sequence.
 37. The system of claim 31, wherein said generation of said sequence comprises insertion of said one or more pilot symbols at pseudorandom intervals among said one or more information symbols.
 38. The system of claim 31, wherein said sequence comprises K consecutive pilot symbols every N information symbols, where K and N are each a positive integer greater than one.
 39. The system of claim 31, wherein: said generation of said sequence comprises a determination of how many of said one or more pilot symbols to insert in said sequence based on one or more performance indicators from a receiver to which said sequence is to be transmitted.
 40. The system of claim 39, wherein said one or more performance indicators comprise signal-to-noise ratio. 